View EL5246CN_255006.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

(R)
EL5144, EL5146, EL5244, EL5246, EL5444
Data Sheet April 13, 2005 FN7177.1
100MHz Single-Supply Rail-to-Rail Amplifiers
The EL5144 series amplifiers are voltage-feedback, high speed, rail-to-rail amplifiers designed to operate on a single +5V supply. They offer unity gain stability with an unloaded 3dB bandwidth of 100MHz. The input common-mode voltage range extends from the negative rail to within 1.5V of the positive rail. Driving a 75 double terminated coaxial cable, the EL5144 series amplifiers drive to within 150mV of either rail. The 200V/s slew rate and 0.1%/0.1 differential gain/differential phase makes these parts ideal for composite and component video applications. With their voltagefeedback architecture, these amplifiers can accept reactive feedback networks, allowing them to be used in analog filtering applications These amplifiers will source 90mA and sink 65mA. The EL5146 and EL5246 have a power-savings disable feature. Applying a standard TTL low logic level to the CE (Chip Enable) pin reduces the supply current to 2.6A within 10ns. Turn-on time is 500ns, allowing true break-beforemake conditions for multiplexing applications. Allowing the CE pin to float or applying a high logic level will enable the amplifier. For applications where board space is critical, singles are offered in a 5-pin SOT-23 package, duals in 8- and 10-pin MSOP packages, and quads in a 16-pin QSOP package. Singles, duals, and quads are also available in industrystandard pinouts in SO and PDIP packages. All parts operate over the industrial temperature range of -40C to +85C.
Features
* Rail-to-rail output swing * -3dB bandwidth = 100MHz * Single-supply +5V operation * Power-down to 2.6A * Large input common-mode range 0V < VCM < 3.5V * Diff gain/phase = 0.1%/0.1 * Low power 35mW per amplifier * Space-saving SOT23-5, MSOP8 & 10, & QSOP16 packages * Pb-Free available (RoHS compliant)
Applications
* Video amplifiers * 5V analog signal processing * Multiplexers * Line drivers * Portable computers * High speed communications * Sample & hold amplifiers * Comparators
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-352-6832 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2003, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners.
EL5144, EL5146, EL5244, EL5246, EL5444 Ordering Information
PART NUMBER EL5144CW-T7 EL5144CW-T7A EL5144CWZ-T7 (See Note) EL5144CWZ-T7A (See Note) EL5146CN EL5146CS EL5146CS-T7 EL5146CS-T13 EL5146CSZ (See Note) EL5146CSZ-T7 (See Note) EL5146CSZ-T13 (See Note) EL5244CN EL5244CS EL5244CS-T7 EL5244CS-T13 EL5244CSZ (See Note) EL5244CSZ-T7 (See Note) EL5244CSZ-T13 (See Note) EL5244CY EL5244CY-T13 EL5244CYZ (See Note) EL5244CYZ-T7 (See Note) EL5244CYZ-T13 (See Note) EL5246CN EL5246CS EL5246CS-T7 EL5246CS-T13 EL5246CSZ (See Note) EL5246CSZ-T7 (See Note) EL5246CSZ-T13 (See Note) EL5246CY EL5246CY-T13 PACKAGE 5-Pin SOT-23* 5-Pin SOT-23* 5-Pin SOT-23* (Pb-free) 5-Pin SOT-23* (Pb-free) 8-Pin PDIP 8-Pin SOIC 8-Pin SOIC 8-Pin SOIC 8-Pin SOIC (Pb-free) 8-Pin SOIC (Pb-free) 8-Pin SOIC (Pb-free) 8-Pin PDIP 8-Pin SOIC 8-Pin SOIC 8-Pin SOIC 8-Pin SOIC (Pb-free) 8-Pin SOIC (Pb-free) 8-Pin SOIC (Pb-free) 8-Pin MSOP 8-Pin MSOP 8-Pin MSOP (Pb-free) 8-Pin MSOP (Pb-free) 8-Pin MSOP (Pb-free) 14-Pin PDIP 14-Pin SOIC 14-Pin SOIC 14-Pin SOIC 14-Pin SOIC (Pb-free) 14-Pin SOIC (Pb-free) 14-Pin SOIC (Pb-free) 10-Pin MSOP 10-Pin MSOP TAPE & REEL PKG. DWG. # 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" 13" 7" 13" 7" 13" 7" 13" 13" 7" 13" 7" 13" 7" 13" 13" MDP0038 MDP0038 MDP0038 MDP0038 MDP0031 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0031 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0043 MDP0043 MDP0043 MDP0043 MDP0043 MDP0031 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0043 MDP0043
Ordering Information (Continued)
PART NUMBER EL5246CYZ (See Note) EL5246CYZ-T7 (See Note) EL5246CYZ-T13 (See Note) EL5444CN EL5444CS EL5444CS-T7 EL5444CS-T13 EL5444CSZ (See Note) EL5444CSZ-T7 (See Note) EL5444CSZ-T13 (See Note) EL5444CU EL5444CU-T13 EL5444CUZ (See Note) EL5444CUZ-T7 (See Note) EL5444CUZ-T13 (See Note) PACKAGE 10-Pin MSOP (Pb-free) 10-Pin MSOP (Pb-free) 10-Pin MSOP (Pb-free) 14-Pin PDIP 14-Pin SOIC 14-Pin SOIC 14-Pin SOIC 14-Pin SOIC (Pb-free) 14-Pin SOIC (Pb-free) 14-Pin SOIC (Pb-free) 16-Pin QSOP 16-Pin QSOP 16-Pin QSOP (Pb-free) 16-Pin QSOP (Pb-free) 16-Pin QSOP (Pb-free) TAPE & REEL PKG. DWG. # 7" 13" 7" 13" 7" 13" 13" 7" 13" MDP0043 MDP0043 MDP0043 MDP0031 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0040 MDP0040 MDP0040 MDP0040 MDP0040
*EL5144CW symbol is .Jxxx where xxx represents date NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
2
EL5144, EL5146, EL5244, EL5246, EL5444 Pinouts
EL5144 (5-PIN SOT-23) TOP VIEW
OUT 1 5 VS NC 1
s
EL5146 & EL5146 (8-PIN SO, PDIP) TOP VIEW
8 CE
GND
2 + 4 IN-
IN-
2
+
7
VS
IN+
3
IN+
3
6
OUT
GND
4
5
NC
EL5244 (8-PIN SOIC, PDIP, MSOP) TOP VIEW
OUTA INAINA+ 1 8 VS OUTB INBINB+ INA+ CEA 1
EL5246 (10-PIN MSOP) TOP VIEW
10 INA+ 9 OUTA VS OUTB INBINA+ NC
EL5246 (14-PIN SOIC, PDIP) TOP VIEW
1 + 14 INA13 OUTA 12 NC
2
+
7
2
2
3 +
6
GND
3 + -
8
CEA
3
GND
4
5
CEB
4
7
GND
4
11 VS 10 NC + -
INB+
5
6
CEB
5
NC
6
9
OUTB INB-
INB+
7
8
EL5444 (14-PIN SOIC, PDIP) TOP VIEW
OUTA INA1 14 OUTD OUTA INA1
EL5444 (16-PIN QSOP) TOP VIEW
16 OUTD
+
+
INA+
-
2
13
IND-
2
15 IND14 IND+
+
+
-
3
12
IND+
INA+
3
VS INB+
4
11
GND
VS VS INB+
4
-
-
13 GND
5
10
INC+
5
12 GND
INB-
6
9
INC-
6
11 INC+ + + 10 INC-
+
+
-
OUTB
7
8
OUTC
OUTB
8
-
-
INB-
7
-
9
OUTC
3
EL5144, EL5146, EL5244, EL5246, EL5444
Absolute Maximum Ratings (TA = 25C)
Supply Voltage between VS and GND . . . . . . . . . . . . . . . . . . . . .+6V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40C to +85C
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER AC PERFORMANCE dG dP BW
VS = +5V, GND = 0V, TA = 25C, CE = +2V, unless otherwise specified. CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
Differential Gain Error (Note 1) Differential Phase Error (Note 1) Bandwidth
G = 2, RL = 150 to 2.5V, RF = 1k G = 2, RL = 150 to 2.5V, RF = 1k -3dB, G = 1, RL = 10k, RF = 0 -3dB, G = 1, RL = 150, RF = 0
0.1 0.1 100 60 8 60
% MHz MHz MHz MHz V/s ns
BW1 GBWP SR tS
Bandwidth Gain Bandwidth Product Slew Rate Settling Time
0.1dB, G = 1, RL = 150 to GND, RF = 0
G = 1, RL = 150 to GND, RF = 0, VO = 0.5V to 3.5V to 0.1%, VOUT = 0V to 3V
150
200 35
DC PERFORMANCE AVOL Open Loop Voltage Gain RL = no load, VOUT = 0.5V to 3V RL = 150 to GND, VOUT = 0.5V to 3V VOS Offset Voltage VCM = 1V, SOT23-5 and MSOP packages VCM = 1V, All other packages TCVOS IB Input Offset Voltage Temperature Coefficient Input Bias Current VCM = 0V & 3.5V 10 2 100 54 40 65 50 25 15 dB dB mV mV mV/C nA
INPUT CHARACTERISTICS CMIR CMRR Common Mode Input Range Common Mode Rejection Ratio CMRR 47dB DC, VCM = 0 to 3.0V DC, VCM = 0 to 3.5V RIN CIN Input Resistance Input Capacitance 0 50 47 60 60 1.5 1.5 3.5 V dB dB G pF
OUTPUT CHARACTERISTICS VOP Positive Output Voltage Swing RL = 150 to 2.5V (Note 2) RL = 150 to GND (Note 2) RL = 1k to 2.5V (Note 2) VON Negative Output Voltage Swing RL = 150 to 2.5V (Note 2) RL = 150 to GND (Note 2) RL = 1k to 2.5V (Note 2) +IOUT -IOUT Positive Output Current Negative Output Current RL = 10 to 2.5V RL = 10 to 2.5V 60 -50 4.70 4.20 4.95 4.85 4.65 4.97 0.15 0 0.03 90 -65 0.05 120 -80 0.30 V V V V V V mA mA
ENABLE (EL5146 & EL5246 ONLY)
4
EL5144, EL5146, EL5244, EL5246, EL5444
Electrical Specifications
PARAMETER tEN tDIS IIHCE IILCE VIHCE VILCE SUPPLY IsON IsOFF PSOR PSRR NOTES: 1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.8MHz, VOUT is swept from 0.8V to 3.4V, RL is DC-coupled. 2. RL is total load resistance due to feedback resistor and load resistor. Supply Current - Enabled (per amplifier) Supply Current - Disabled (per amplifier) Power Supply Operating Range Power Supply Rejection Ratio DC, VS = 4.75V to 5.25V No load, VIN = 0V, CE = 5V No load, VIN = 0V, CE = 0V 4.75 50 7 2.6 5.0 60 8.8 5 5.25 mA mA V dB Enable Time Disable Time CE pin Input High Current CE pin Input Low Current VS = +5V, GND = 0V, TA = 25C, CE = +2V, unless otherwise specified. (Continued) CONDITIONS EL5146, EL5246 EL5146, EL5246 CE = 5V, EL5146, EL5246 CE = 0V, EL5146, EL5246 2.0 0.8 MIN TYP 500 10 0.003 -1.2 1 -3 MAX UNIT ns ns mA mA V V
DESCRIPTION
CE pin Input High Voltage for Power EL5146, EL5246 Up CE pin Input Low Voltage for Power EL5146, EL5246 Down
5
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
Non-Inverting Frequency Response (Gain) 2 AV=1, RF=0 Normalized Magnitude (dB) 0 AV=2, RF=1k Phase () -2 AV=5.6, RF=1k -4 -45 AV=5.6, RF=1k 0 AV=1, RF=0 Non-Inverting Frequency Response (Phase)
-90
AV=2, RF=1k
-135 -6 VCM=1.5V RL=150 -8 1M 10M Frequency (Hz) 100M -180 1M VCM=1.5V RL=150 10M Frequency (Hz) 100M
Inverting Frequency Response (Gain) 2 180 Normalized Magnitude (dB) 0 AV=-1 135 Phase () -2 AV=-5.6 -4 AV=-2
Inverting Frequency Response (Phase)
AV=-1
AV=-2 90 AV=-5.6
45 -6 VCM=1.5V RF=1k RL=150 10M Frequency (Hz) 100M VCM=1.5V RF=1k RL=150 10M Frequency (Hz) 100M
0 1M
-8 1M
3dB Bandwidth vs Die Temperature for Various Gains 100 RL=150 80 3dB Bandwidth (MHz) AV=1, RF=0 60 3dB Bandwidth (MHz) 120 150
3dB Bandwidth vs Die Temperature for Various Gains
RL=10k AV=1, RF=0
90
40
AV=2, RF=1k
60 AV=2, RF=1k 30 AV=5.6, RF=1k 0 -55
20
AV=5.6, RF=1k
0 -55
-15
25
65
105
145
-15
25
65
105
145
Die Temperature (C)
Die Temperature (C)
6
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Frequency Response for Various RL VCM=1.5V RF=0 AV=1 RL=10k
Frequency Response for Various CL VCM=1.5V RL=150 AV=1 CL=100pF CL=47pF
4 Normalized Magnitude (dB)
8 Normalized Magnitude (dB)
2
4
0 RL=520 -2 RL=150 -4 1M 10M Frequency (Hz) Frequency Response for Various RF and RG 100M
0 CL=22pF -4 CL=0pF
-8 1M 10M Frequency (Hz) Group Delay vs Frequency 10 100M
2 Normalized Magnitude (dB) RF=RG=1k 0
RF=RG=2k 8 Group Delay (ns)
AV=2 RF=1k
6
-2
RF=RG=560
4
-4 VCM=1.5V RL=150 AV=2 10M Frequency (Hz) Open Loop Gain and Phase vs Frequency 0 80 Phase 90 40 RL=150 135 20 Gain 180 0 1k 10k 100k 1M 10M 225 100M Phase () RL=1k 60 100M
AV=1 RF=1
2
-6 1M
0 1M
10M Frequency (Hz)
100M
Open Loop Voltage Gain vs Die Temperature 80
Open Loop Gain (dB)
45
70 No Load 60
Gain (dB)
50 RL=150 40
30 -55
-15
25
65
105
145
Frequency (Hz)
Die Temperature (C)
7
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Voltage Noise vs Frequency - Video Amp 10k 200
Closed Loop Output Impedance vs Frequency RF=0 AV=2
Voltage Noise (nV/Hz)
Closed Loop (ZO) 100 10k 100M
1k
20
2
100
0.2 10 10 1k 100k 1M 10M 10k 100k 1M Frequency (Hz) PSRR and CMRR vs Frequency 20 12 0 Offset Voltage (mV) 6 PSRR, CMRR (dB) CMRR -20 PSRR-40 10M 100M
Frequency (Hz) Offset Voltage vs Die Temperature (6 Typical Samples)
0
-6
-60 -12 -55 -15 25 65 105 145 -80 1k 10k 100k
PSRR+
1M
10M
100M
Die Temperature (C) Output Voltage Swing vs Frequency for THD < 1% 5 Output Voltage Swing (VPP) Output Voltage Swing (VPP) RF=1k AV=2 4 RL=500 to 2.5V RL=150 to 2.5V 2 5 RF=1k AV=2 4
Frequency (Hz) Output Voltage Swing vs Frequency for THD < 0.1%
3
3 RL=500 to 2.5V 2
1
1 RL=150 to 2.5V 0 1M 10M Frequency (Hz) 100M
0 1M
10M Frequency (Hz)
100M
8
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Large Signal Pulse Response (Single Supply) 4 VS=5V RL=150 to 0V RF=1k AV=2 1.9
Small Signal Pulse Response (Single Supply) VS=5V RL=150 to 0V RF=1k AV=2
Output Voltage (V)
2
Output Voltage (V)
3
1.7
1.5
1
1.3
0 Time (20ns/div)
1.1 Time (20ns/div)
Large Signal Pulse Response (Split Supplies) 4 VS=2.5V RL=150 to 0V RF=1k AV=2 0.4
Small Signal Pulse Response (Split Supply) VS=2.5V RL=150 to 0V RF=1k AV=2
Output Voltage (V)
0
Output Voltage (V)
2
0.2
0
-2
-0.2
-4 Time (20ns/div)
-0.4 Time (20ns/div)
Settling Time vs Settling Accuracy 100 RL=1k RF=500 AV=-1 VSTEP=3V 250
Slew Rate vs Die Temperature
80 Settling Time (ns)
60
Slew Rate (V/s)
200
40
20
0 0.01
0.1 Settling Accuracy (%)
1
150 -55
-15
25
65
105
145
Die Temperature (C)
9
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Differential Gain for RL Tied to 0V RF=0 AV=1 Differential Phase ()
Differential Phase for RL Tied to 0V RF=0 AV=1
0.08 Differential Gain (%)
0.2
0.04 RL=10k 0 RL=150 -0.04
0.1 RL=10k 0 RL=150 -0.1
-0.08 0.25 1.75 VOUT (V) Differential Gain for RL Tied to 2.5V RF=0 AV=1 Differential Phase () 3.25
-0.2 0.25 1.75 VOUT (V) Differential Phase for RL Tied to 2.5V RF=0 AV=1 3.25
0.2 Differential Gain (%)
0.2
0.1
0.1 RL=10k 0
0 RL=10k -0.1 RL=150
-0.1 RL=150 -0.2
-0.2 0.5 2 VOUT (V) Differential Gain for RL Tied to 0V RF=1k AV=2 Differential Phase () 3.5
0.5
2 VOUT (V)
3.5
Differential Phase for RL Tied to 0V RF=1k AV=2
0.2 Differential Gain (%)
RL=150
0.2
RL=150
0.1
0.1
0
RL=10k
0
RL=10k
-0.1
-0.1
-0.2 0.5 2 VOUT (V) 3.5
-0.2 0.5 2 VOUT (V) 3.5
10
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Differential Gain for RL Tied to 2.5V RF=1k AV=2 Differential Phase ()
Differential Phase for RL Tied to 2.5V RF=1k AV=2 RL=10k
0.2 Differential Gain (%)
0.2
0.1
RL=150
0.1
0
0 RL=150
-0.1
RL=10k
-0.1
-0.2 0.5 2 VOUT (V) 2nd and 3rd Harmonic Distortion vs Frequency -25 3.5
-0.2 0.5 2 VOUT (V) 2nd and 3rd Harmonic Distortion vs Frequency -25 HD3 3.5
-35 Distortion (dBc)
HD3 Distortion (dBc) HD2
-35
-45
-45 HD2 -55
-55
-65 VOUT=0.25V to 2.25V RL=100 to 0V 10M Frequency (Hz) 2nd and 3rd Harmonic Distortion vs. Frequency -25 HD3 Crosstalk (dB) 100M
-65 VOUT=0.5V to 2.5V RL=100 to 0V 10M Frequency (Hz) Channel to Channel Crosstalk - Duals and Quads (Worst Channel) 0 100M
-75 1M
-75 1M
-35 Distortion (dBc)
-20
-45 HD2
-40
-55
-60
-65 VOUT=1V to to VOUT=1V 3V =100 to 0V RL3V 10M Frequency (Hz) 100M
-80
-75 1M
-100 100k
1M
10M
100M
Frequency (Hz)
11
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Supply Current (per Amp) vs Supply Voltage 120 8 100 Supply Current (mA) 6 Output Current (mA)
Output Current vs Die Temperature RL=10 to 2.5V
Source 80
4
60 Sink 40
2
0 0 1 2 3 4 5 20 -55 -15 25 65 105 145
Supply Voltage (V) Supply Current - ON (per Amp) vs Die Temperature 9 5
Die Temperature (C) Supply Current - OFF (per Amp) vs Die Temperature
8 Supply Current (mA) Supply Current (A) 25
4
7
3
6
2
5
1
4 -55
-15
65
105
145
0 -55
-15
25
65
105
145
Die Temperature (C) Positive Output Voltage Swing vs Die Temperature 5 RL=150 4.9 Output Voltage (V) RL=150 to 2.5V 4.8 Output Voltage (V) 0.4 0.5
Die Temperature (C) Negative Output Voltage Swing vs Die Temperature
0.3 RL=150 to 2.5V
4.7 RL=150 to 0V 4.6
0.2
0.1 RL=150 to 0V
4.5 -55
-15
25
65
105
145
0 -55
-15
25
65
105
145
Die Temperature (C)
Die Temperature (C)
12
EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves
(Continued)
Output Voltage from Either Rail vs Die Temperature for Various Effective RLOAD 300
Effective RLO 50 AD=1
OFF Isolation - EL5146 & EL5246 -20 EL5146CS & EL5146CN
100 Output Voltage (V)
-40 Magnitude (dBc)
-60
Effective RLOAD=1k
EL5246CS
10
Effective RLOAD=5k
-80 EL5246CN -100
1 -55
Effective RLOAD = RL//RF to VS/2 -15 25 65 105 145
-120 10k
100k
1M Frequency (Hz)
10M
100M
Die Temperature (C)
Maximum Power Dissipation vs. Ambient Temperature Singles (TJMAX = 150C) 2.0 PDIP, JA = 110C/W SOIC, JA = 161C/W 1.2 Power Dissipation (W) 2.5
Maximum Power Dissipation vs. Ambient Temperature Duals (TJMAX = 150C)
Power Dissipation (W)
1.6
2.0
PDIP-14, JA = 87C/W PDIP-8, JA = 107C/W SOIC-14, JA = 120C/W
1.5
0.8
1.0
0.4 SOT23-5, JA = 256C/W 0 -50
0.5
SOIC-8, JA = 159C/W MSOP-8,10, JA = 206C/W -20 10 40 70 100
-20
10
40
70
100
0 -50
Ambient Temperature (C)
Ambient Temperature (C)
Maximum Power Dissipation vs. Ambient Temperature Quads (TJMAX = 150C) 2.5 PDIP-14, JA = 83C/W
Power Dissipation (W)
2.0
1.5
1.0 SOIC-14, JA = 118C/W QSOP-16, JA = 158C/W 0 -50 -20 10 40 70 100
0.5
Ambient Temperature (C)
13
EL5144, EL5146, EL5244, EL5246, EL5444 Pin Descriptions
5-PIN SOT23 5 2 8-PIN SO/PDIP/ 8-PIN MSOP SO/PDIP 7 4 8 4 16-PIN MSOP 8 3 14-PIN 14-PIN SO/PDIP SO/PDIP 11 4 4 11 16-PIN QSOP 4,5 12,13 NAME VS GND FUNCTION Positive Power Supply Ground or Negative Power Supply Noninverting Input
VS
EQUIVALENT CIRCUIT
3
3
IN+
GND
Circuit 1 4 1 2 6 INOUT Inverting Input Amplifier Output
VS
(Reference Circuit 1)
GND
Circuit 2 3 1 1 3 3 INA+ Amplifier A Noninverting Input Amplifier A Inverting Input Amplifier A Output Amplifier B Noninverting Input Amplifier B Inverting Input Amplifier B Output Amplifier C Noninverting Input Amplifier C Inverting Input Amplifier C Output Amplifier D Noninverting Input Amplifier D Inverting Input (Reference Circuit 1)
2 1 5
10 9 5
14 13 7
2 1 5
2 1 6
INAOUTA INB+
(Reference Circuit 1) (Reference Circuit 2) (Reference Circuit 1)
6 7
6 7
8 9
6 7 10
7 8 11
INBOUTB INC+
(Reference Circuit 1) (Reference Circuit 2) (Reference Circuit 1)
9 8 12
10 9 14
INCOUTC IND+
(Reference Circuit 1) (Reference Circuit 2) (Reference Circuit 1)
13
15
IND-
(Reference Circuit 1)
14
EL5144, EL5146, EL5244, EL5246, EL5444 Pin Descriptions
5-PIN SOT23 (Continued)
8-PIN SO/PDIP/ 8-PIN MSOP SO/PDIP
16-PIN MSOP
14-PIN 14-PIN SO/PDIP SO/PDIP 14
16-PIN QSOP 16
NAME OUTD CE
FUNCTION Amplifier D Output Enable (Enabled when high)
EQUIVALENT CIRCUIT (Reference Circuit 2)
8
VS
+ - GND
1.4V
Circuit 3 2 3 CEA Enable Amplifier (Reference Circuit 3) A (Enabled when high) Enable Amplifier (Reference Circuit 3) B (Enabled when high) No Connect. Not internally connected.
4
5
CEB
1,5
2,6, 10,12
NC
Description of Operation and Applications Information
Product Description
The EL5144 series is a family of wide bandwidth, single supply, low power, rail-to-rail output, voltage feedback operational amplifiers. The family includes single, dual, and quad configurations. The singles and duals are available with a power down pin to reduce power to 2.6A typically. All the amplifiers are internally compensated for closed loop feedback gains of +1 or greater. Larger gains are acceptable but bandwidth will be reduced according to the familiar GainBandwidth Product. Connected in voltage follower mode and driving a high impedance load, the EL5144 series has a -3dB bandwidth of 100MHz. Driving a 150 load, they have a -3dB bandwidth of 60MHz while maintaining a 200V/s slew rate. The input common mode voltage range includes ground while the output can swing rail to rail.
suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the GND pin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to a minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance.
Input, Output, and Supply Voltage Range
The EL5144 series has been designed to operate with a single supply voltage of 5V. Split supplies can be used so long as their total range is 5V. The amplifiers have an input common mode voltage range that includes the negative supply (GND pin) and extends to within 1.5V of the positive supply (VS pin). They are specified over this range. The output of the EL5144 series amplifiers can swing rail to rail. As the load resistance becomes lower in value, the ability to drive close to each rail is reduced. However, even with an effective 150 load resistor connected to a voltage halfway between the supply rails, the output will swing to within 150mV of either rail.
Power Supply Bypassing and Printed Circuit Board Layout
As with any high-frequency device, good printed circuit board layout is necessary for optimum performance. Ground plane construction is highly recommended. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation For normal single supply operation, where the GND pin is connected to the ground plane, a single 4.7F tantalum capacitor in parallel with a 0.1F ceramic capacitor from VS to GND will 15
EL5144, EL5146, EL5244, EL5246, EL5444
Figure 1 shows the output of the EL5144 series amplifier swinging rail to rail with RF = 1k, AV = +2 and RL = 1M. Figure 2 is with RL = 150.
Video Performance
For good video signal integrity, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This can be difficult when driving a standard video load of 150, because of the change in output current with DC level. A look at the Differential Gain and Differential Phase curves for various supply and loading conditions will help you obtain optimal performance. Curves are provided for AV = +1 and +2, and RL = 150 and 10k tied both to ground as well as 2.5V. As with all video amplifiers, there is a common mode sweet spot for optimum differential gain/differential phase. For example, with AV = +2 and RL = 150 tied to 2.5V, and the output common mode voltage kept between 0.8V and 3.2V, dG/dP is a very low 0.1%/0.1. This condition corresponds to driving an AC-coupled, double terminated 75 coaxial cable. With AV = +1, RL = 150 tied to ground, and the video level kept between 0.85V and 2.95V, these amplifiers provide dG/dP performance of 0.05%/0.20. This condition is representative of using the EL5144 series amplifier as a buffer driving a DC coupled, double terminated, 75 coaxial cable. Driving high impedance loads, such as signals on computer video cards, gives similar or better dG/dP performance as driving cables.
5V
0V
FIGURE 1.
5V
Driving Cables and Capacitive Loads
0V
FIGURE 2.
Choice of Feedback Resistor, RF
These amplifiers are optimized for applications that require a gain of +1. Hence, no feedback resistor is required. However, for gains greater than +1, the feedback resistor forms a pole with the input capacitance. As this pole becomes larger, phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF has some maximum value that should not be exceeded for optimum performance. If a large value of RF must be used, a small capacitor in the few picofarad range in parallel with RF can help to reduce this ringing and peaking at the expense of reducing the bandwidth. As far as the output stage of the amplifier is concerned, RF + RG appear in parallel with RL for gains other than +1. As this combination gets smaller, the bandwidth falls off. Consequently, RF also has a minimum value that should not be exceeded for optimum performance. For AV = +1, RF = 0 is optimum. For AV = -1 or +2 (noise gain of 2), optimum response is obtained with RF between 300 and 1k. For AV = -4 or +5 (noise gain of 5), keep RF between 300 and 15k.
The EL5144 series amplifiers can drive 50pF loads in parallel with 150 with 4dB of peaking and 100pF with 7dB of peaking. If less peaking is desired in these applications, a small series resistor (usually between 5 and 50) can be placed in series with the output to eliminate most peaking. However, this will obviously reduce the gain slightly. If your gain is greater than 1, the gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. Another method of reducing peaking is to add a "snubber" circuit at the output. A snubber is a resistor in a series with a capacitor, 150 and 100pF being typical values. The advantage of a snubber is that it does not draw DC load current. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5144 series amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can reduce peaking.
Disable/Power-Down
The EL5146 and EL5246 amplifiers can be disabled, placing its output in a high-impedance state. Turn off time is only 10ns and turn on time is around 500ns. When disabled, the amplifier's supply current is reduced to 2.6A typically, thereby effectively eliminating power consumption. The amplifier's power down can be controlled by standard TTL or CMOS signal levels at the CE pin. The applied logic signal is
16
EL5144, EL5146, EL5244, EL5246, EL5444
relative to the GND pin. Letting the CE pin float will enable the amplifier. Hence, the 8-pin PDIP and SOIC single amps are pin compatible with standard amplifiers that don't have a power down feature. If we set the two PDMAX equations equal to each other, we can solve for RL:
V OUT x ( V S - V OUT ) R L = -------------------------------------------------------------------------------------------- T JMAX - T AMAX -------------------------------------------- - ( V S x I SMAX ) N x JA
Short Circuit Current Limit
The EL5144 series amplifiers do not have internal short circuit protection circuitry. Short circuit current of 90mA sourcing and 65mA sinking typically will flow if the output is trying to drive high or low but is shorted to half way between the rails. If an output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. Maximum reliability is maintained if the output current never exceeds 50mA. This limit is set by internal metal interconnect limitations. Obviously, short circuit conditions must not remain or the internal metal connections will be destroyed.
Assuming worst case conditions of TA = +85C, VOUT = VS/2V, VS = 5.5V, and ISMAX = 8.8mA per amplifier, below is a table of all packages and the minimum RL allowed.
PART EL5144CW EL5146CS EL5146CN EL5244CS PACKAGE SOT23-5 SOIC-8 PDIP-8 SOIC-8 PDIP-8 MSOP-8 MSOP-10 SOIC-14 PDIP-14 QSOP-16 SOIC-14 PDIP-14 MINIMUM RL 37 21 14 48 30 69 69 34 23 139 85 51
Power Dissipation
With the high output drive capability of the EL5144 series amplifiers, it is possible to exceed the 150C Absolute Maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if load conditions or package type need to be modified for the amplifier to remain in the safe operating area. The maximum power dissipation allowed in a package is determined according to:
T JMAX - T AMAX PD MAX = ------------------------------------------- JA
EL5244CN EL5244CY EL5246CY EL5246CS EL5246CN EL5444CU EL5444CS EL5444CN
EL5144 Series Comparator Application
The EL5144 series amplifier can be used as a very fast, single supply comparator. Most op amps used as a comparator allow only slow speed operation because of output saturation issues. The EL5144 series amplifier doesn't suffer from output saturation issues. Figure 3 shows the amplifier implemented as a comparator. Figure 4 is a
where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature JA = Thermal resistance of the package PDMAX = Maximum power dissipation in the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or:
V OUT PD MAX = N x V S x I SMAX + ( V S - V OUT ) x --------------R
L
where: N = Number of amplifiers in the package VS = Total supply voltage ISMAX = Maximum supply current per amplifier VOUT = Maximum output voltage of the application RL = Load resistance tied to ground 17
EL5144, EL5146, EL5244, EL5246, EL5444
graph of propagation delay vs. overdrive as a square wave is presented at the input of the comparator.
+5V 1 EL5146 VIN +2.5V 4 5 + - 2 3 + 7 6 VOUT RL 3 EL5246 4 Select 5 6 Propagation Delay vs. Overdrive for Amplifier Used as a Comparator 1000 VIN 2 2.4VPP 5MHz 7 + 10 9 150 8 4.7F 0.1F 11 8 0.1F
directly together. Isolation resistors at each output are not necessary.
VIN 1 3VPP 10MHz
1 2 +
14 13 12 +5V VOUT
FIGURE 3.
FIGURE 5.
Propagation Delay (ns)
Negative Going Signal 100 VOUT Positive Going Signal
5V
10 0.01 0.1 Overdrive (V) 1.0 Select
0V 5V 0V
FIGURE 4.
Multiplexing with the EL5144 Series Amplifier
Besides normal power down usage, the CE pin on the EL5146 and EL5246 series amplifiers also allow for multiplexing applications. Figure 5 shows an EL5246 with its outputs tied together, driving a back terminated 75 video load. A 3VP-P 10MHz sine wave is applied at Amp A input, and a 2.4VP-P 5MHz square wave to Amp B. Figure 6 shows the SELECT signal that is applied, and the resulting output waveform at VOUT. Observe the break-before-make operation of the multiplexing. Amp A is on and VIN1 is being passed through to the output of the amplifier. Then Amp A turns off in about 10ns. The output decays to ground with an RLCL time constants. 500ns later, Amp B turns on and VIN2 is passed through to the output. This break-before-make operation ensures that more than one amplifier isn't trying to drive the bus at the same time. Notice the outputs are tied
FIGURE 6.
Free Running Oscillator Application
Figure 7 is an EL5144 configured as a free running oscillator. To first order, ROSC and COSC determine the frequency of oscillation according to:
0.72 F OSC = --------------------------------------R OSC x C OSC
For rail to rail output swings, maximum frequency of oscillation is around 15MHz. If reduced output swings are acceptable, 25MHz can be achieved. Figure 8 shows the
18
EL5144, EL5146, EL5244, EL5246, EL5444
oscillator for ROSC = 510, COSC = 240pF and FOSC = 6MHz.
470K +5V
1 470K 2 3 470K +
5 0.1F 4 COSC ROSC
FIGURE 7.
5V
VOUT
0V
FIGURE 8.
5V
0V
FIGURE 9.
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 19

▲Up To Search▲

Price & Availability of EL5246CN

	To Download EL5246CN Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .